High-frequency piezoelectric oscillator

ABSTRACT

In the high-frequency piezoelectric oscillator, capacitors C 1 , C 2  as a part of a load capacitor are connected between a base of a transistor TR 1  and the ground. The connection point of the capacitors C 1 , C 2  is connected to an emitter of the transistor TR 1,  and is grounded via an emitter resistor R 1 . A base bias circuit consisting of resistors RB 1  and RB 2  is connected to the base of the transistor TR 1.  A piezoelectric vibrator, an inductor, and a resistor are connected in parallel, and connected between the base of the transistor TR 1.  A capacitor is connected to the parallel circuit and grounded. A collector of the transistor and a power supply line are connected together.

BACKGROUND OF THE INVENTION

[0001] 1. Field of the Invention

[0002] The present invention relates to a high-frequency piezoelectricoscillator, and more particularly, to a high-frequency piezoelectricoscillator having en excellent stabilization characteristics withsuppressing unwanted resonance.

[0003] 2. Description of the Related Art

[0004] Conventionally, an odd-order overtone, for example, third, fifth,and seventh-overtone of a vibrator is utilized to obtain oscillation inhigh frequency. In order to obtain the overtone oscillation, a harmonicselection circuit having high negative resistance at a desired frequencyis provided in the oscillation circuit. FIG. 22 illustrates one exampleof a conventional Colpitts type oscillator. A capacitor C11 that becomesa part of a load capacitance of the oscillation circuit is connectedbetween a base and an emitter of a transistor TR11. A parallel resonancecircuit consisting of a capacitor C12 and an inductor L11 is connectedto the emitter of the transistor TR11. A parallel circuit of a capacitor13 and an emitter resistor R11 are connected in series to the parallelresonance circuit, and are grounded. A base bias circuit consisting of aresistor RB11 and a resistor RB12 is connected to a base of thetransistor TR11. A series circuit of a piezoelectric vibrator (X′tal)and a capacitor C14 is connected between the base of the transistor TR11and the ground. A collector of the transistor TR11 and a power supplyline (VCC) are connected together.

[0005] In the present circuit, an oscillation output cannot be obtainedwhen a desired frequency becomes 600 MHz or above. That is, theresonance frequency of a parallel resonance circuit comprised of thecapacitor C12 and the inductor L11 can be set to a desired level,however, when the frequency is 600 MHz or above, an impedance of thepiezoelectric vibrator lowers due to an interelectrode capacitance C0 ofthe piezoelectric vibrator. Accordingly, sufficient negative resistancecannot be generated in an oscillation loop of the oscillation circuit.To overcome this difficulty, as shown in FIG. 23, the inductor L20 isinserted in parallel into the piezoelectric vibrator (X′tal). Theinterelectrode capacitance C0 is canceled by matching the parallelresonance frequency of the interelectrode capacitance C0 and theinductor L20 with the oscillation frequency. Since the parallel circuitof the interelectrode capacitance C0 and the inductor L20 preventsdeterioration of the negative resistance of the oscillation circuit andprovides high selectivity, a high frequency oscillation can be achieved.

[0006] In order to make clear a difference between the present inventionand the conventional circuit, the circuit shown in FIG. 23 will beexplained in further detail. According to the conventional circuit,capacitors C21 and C22 that form a part of the negative capacitor areconnected between the base of the transistor TR21 and the ground. Theconnection point of the capacitors C21 and C22 is connected to anemitter of the transistor TR21, and is grounded via a resistor R21. Abase bias circuit consisting of a resistor RB21 and a resistor RB22 isconnected to abase of the transistor TR21. A parallel circuit of thepiezoelectric vibrator (X′tal) and the inductor L20 is connected to acapacitor C23, and a series circuit of the parallel circuit and thecapacitor is connected between the base of the transistor TR21 and theground. Further, a collector of the transistor TR21 and the power supplyline (Vcc) are connected.

[0007]FIG. 24 illustrates an equivalent circuit model of theconventional circuit shown in FIG. 23. In FIG. 24, the piezoelectricvibrator is indicated by the equivalent circuit comprising a reactanceL1, capacitance C1, C0, and resistance R1, and an oscillation circuit isindicated by negative resistance −Rc and reactance Xc. FIG. 26illustrates another equivalent circuit model of the conventional circuitin which a reactance of a parallel resonance circuit comprised of thecapacitance C0 and inductance L0 shown in FIG. 24 is presented as X0.

[0008] Expressions for an oscillation condition are as follows.$\begin{matrix}\begin{matrix}{{X_{c} = \frac{1}{\omega \cdot C_{c}}},\quad {\ldots \quad X_{0}}} \\{{= \frac{1}{\omega \cdot {C_{0}\left( {\frac{\omega_{0}^{2}}{\omega^{2}} - 1} \right)}}},\quad {\ldots \quad C_{\alpha}}} \\{{{= {C_{0}\left( {1 - \frac{\omega_{0}^{2}}{\omega^{2}}} \right)}},\quad {{\ldots \quad C_{L}} = {- \frac{1}{\omega \cdot X_{L}}}},}\quad}\end{matrix} & (1) \\\begin{matrix}{{{\ldots \quad X_{c}} = \frac{1}{\omega \cdot C_{c}}},\quad {\ldots \quad X_{0}}} \\{{= {{\frac{1}{\omega \cdot C_{0}}\quad \left( {\frac{\omega^{2}}{\omega_{0}^{2}} - 1} \right)\quad \ldots \quad R_{L}} = \frac{{- R_{c}}X_{0}^{2}}{R_{c}^{2} + \left( {X_{0} - X_{c}} \right)^{2}}}},\quad {\ldots \quad X_{L}}} \\{= \frac{X_{0}\left\{ {R_{c}^{2} - {X_{c}\left( {X_{0} - X_{c}} \right)}} \right\}}{R_{c}^{2} + \left( {X_{0} - X_{c}} \right)^{2}}}\end{matrix} & (2) \\\begin{matrix}{{{{\ldots \quad R_{1}} + R_{L}} = 0}\quad} \\{{{{\cdot \omega}\quad L_{1}} + \frac{1}{\omega \cdot C_{1}} + X_{L}} = 0}\end{matrix} & (3)\end{matrix}$

[0009]FIG. 25 illustrates a result of carrying out a simulation aboutcharacteristics of negative resistance Rc and capacitance Cc of aconventional Colpitts oscillation circuit. The axis of ordinatesrepresents negative resistance, and the axis of abscissas representsfrequency. From FIG. 25, it is clear that negative resistance does notoccur when the frequency is about 400 MHz or below. However, negativeresistance considerably occurs over 400 MHz frequencies. It can be seenthat negative resistance occurs sufficiently at 2 GHz.

[0010] Impedance ZL is obtained and Exps. (4) and (5) are obtained basedon the equivalent circuit shown in FIG. 26. An Exp. (6) that shows arelationship between the resistance RL and the reactance XL shown inFIG. 27 is obtained from ZL. $\begin{matrix}\begin{matrix}{{{\ldots \quad Z_{L}} = \frac{j\quad {X_{0}\left( {{- R_{c}} - {j\quad X_{c}}} \right)}}{{- R_{c}} - {j\quad X_{c}} + {j\quad X_{0}}}},\quad {{\ldots \quad X_{c}} = \frac{1}{\omega \cdot C_{c}}},\quad {\ldots \quad X_{0}}} \\{{= \frac{1}{\omega \cdot {C_{0}\left( {\frac{\omega_{0}^{2}}{\omega^{2}} - 1} \right)}}}\quad}\end{matrix} & (4) \\\begin{matrix}{\ldots = \frac{\quad {X_{0}\left( {X_{0} - {j\quad R_{c}}} \right)}}{{- R_{c}} + {j\quad \left( {X_{0} - \quad X_{c}} \right)}}} \\{= \frac{\quad {{X_{0}\left( {X_{c} - {j\quad R_{c}}} \right)}\left\{ {{- R_{c}} - {j\left( {X_{0} - X_{c}} \right)}} \right\}}}{R_{c}^{2} + \left( {X_{0} - \quad X_{c}} \right)^{2}}} \\{{= {\frac{\quad {{- {X_{0}\left( {X_{c} - {j\quad R_{c}}} \right)}}\left\{ {R_{c} + {j\left( {X_{0} - X_{c}} \right)}} \right\}}}{R_{c}^{2} + \left( {X_{0} - \quad X_{c}} \right)^{2}}\quad \ldots}}\quad} \\{{= {\frac{- \quad {X_{0}\left\lbrack {{X_{c}R_{c}} + \quad {R_{c}\left( {X_{0} - X_{c}} \right)} + {j\left\{ {{X_{c}\left( {X_{0} - X_{c}} \right)} - R_{c}^{2}} \right\}}} \right\rbrack}}{R_{c}^{2} + \left( {X_{0} - \quad X_{c}} \right)^{2}}\quad \ldots}}\quad} \\{= \frac{- \quad {X_{0}\left\lbrack {{R_{c}X_{0}} + {j\left\{ {{X_{c}\left( {X_{0} - X_{c}} \right)} - R_{c}^{2}} \right\}}} \right\rbrack}}{R_{c}^{2} + \left( {X_{0} - \quad X_{c}} \right)^{2}}}\end{matrix} & (5) \\\begin{matrix}{{{\ldots \quad R_{L}} = \frac{{- R_{c}}X_{0}^{2}}{R_{c}^{2} + \left( {X_{0} - \quad X_{c}} \right)^{2}}},\quad {\ldots \quad X_{L}}} \\{= \frac{{- X_{0}}\left\{ {{X_{c}\left( {X_{0} - X_{c}} \right)} - R_{c}^{2}} \right\}}{R_{c}^{2} + \left( {X_{0} - \quad X_{c}} \right)^{2}}} \\{{= {\frac{X_{0}\left\{ {R_{c}^{2} - {X_{c}\left( {X_{0} - \quad X_{c}} \right)}} \right\}}{R_{c}^{2} + \left( {X_{0} - \quad X_{c}} \right)^{2}}\quad \ldots \quad R_{L}}}\quad} \\{{= \frac{{- R_{c}}X_{0}^{2}}{R_{c}^{2} + S^{2}}},\quad {\ldots \quad X_{L}}} \\{{= \frac{X_{0}\left\{ {R_{c}^{2} - {X_{c}S}} \right\}}{R_{c}^{2} + S^{2}}},\quad \left. \ldots \quad\Leftarrow \right.,\quad {{...\quad S} = {X_{0} - X_{c}}}}\end{matrix} & (6)\end{matrix}$

[0011]FIG. 28 illustrates characteristics of a load resistance RL shownin FIG. 27. The axis of ordinates represents negative resistance Rc, andthe axis of abscissas represents frequency. From FIG. 28, it is clearthat, a largest negative resistance Rc is −300Ω at 600 MHz. The circuitshown in FIG. 27 constitutes an unwanted oscillation loop shown in FIG.30, and the circuit oscillates in the resonance frequency of reactanceX0+Xc=0. The oscillation loop includes negative resistance −Rc, and hasno factor of anti-negative resistance. Therefore, oscillation occursvery easily. The Exp. (7) represents a frequency condition fω=0. FIG. 31shows a frequency relationship. $\begin{matrix}{{\ldots \quad F} = {{X_{0} + X_{c}} = {{\frac{1}{\omega \cdot {C_{0}\left( {\frac{\omega_{0}^{2}}{\omega} - 1} \right)}} - \frac{1}{\omega \cdot C_{c}}} = 0}}} & (7)\end{matrix}$

[0012]FIG. 31 is a graph of unwanted resonance frequency when ft isCc=3, 5, 10, 30, and 100 pF respectively in a condition that C0=3 pF,the parallel resonance frequency is f0=600 MHz, and the circuit negativeresistance Rc=−100Ω. The frequency when X0−Xc=0 on each characteristiccurve is unwanted resonance frequency.

[0013]FIG. 32 illustrates a relationship between unwanted resonancefrequency and circuit capacitance. The axis of ordinates representsunwanted resonance frequency, and the axis of abscissas representscircuit capacitance. In the present circuit, X0 works as inductor at alow frequency side of the parallel resonance frequency, and this has apossibility of bringing about unwanted oscillation when the inductor isconnected with the circuit capacitance at the circuit side. For example,when the parallel resonance frequency of the interelectrode capacitanceC0 and the inductor L0 is set to 600 MHz and also when C0=3 pF, theparallel resonance frequency is 590 MHz when the circuit capacitanceCc=1 pF, and the parallel resonance frequency is 100 MHz when thecircuit capacitance Cc=100 pF. However, from the above result of thesimulation of negative resistance, there is a possibility thatoscillation occurs at an unwanted resonance point in the vicinity of theparallel resonance frequency. Further, when an extension coil L1 is usedto enlarge a variable range in the oscillation circuit loop, unwantedoscillation occurs in a wide band in connection with a large capacitancegenerated in the vicinity of the resonance point as shown in FIG. 29.

[0014] According to the conventional high-frequency oscillation circuitshown in FIG. 23, unwanted oscillation contributed by the oscillationcircuit and the inductor L20 as explained above is easily occurred.Further more, when an extension coil for expanding a frequency variablerange is inserted into the oscillation loop, unwanted oscillation occurseasily at the parallel resonance frequency defined by the interelectrodecapacitance C0 and the inductor L20. Further, a high negative resistancecannot be obtained easily by the conventional oscillation circuitsexplained the above. Therefore, there are some report regardingexperimental results of the high frequency oscillation circuit, butthere is substantially no success in practical applications.

SUMMARY OF THE INVENTION

[0015] The present invention has been made in the light of the aboveproblems. It is an object of the present invention to provide ahigh-frequency piezoelectric oscillator having high stabilitycharacteristics, and the oscillator suppress unwanted oscillation bydecreasing the interelectrode capacitance C0.

[0016] It is another object of the present invention to provide ahigh-frequency piezoelectric oscillator that can prevent the occurrenceof unwanted oscillation due to the use of an extension coil when theextension coil is provided in an oscillation loop in order to enlargethe oscillation frequency variable range.

[0017] The present invention has been made to solve the above problems.According to a first aspect of the present invention, there is provideda high-frequency piezoelectric oscillator including a piezoelectricoscillator having a piezoelectric element that is excited in apredetermined frequency, and an oscillation amplifier that oscillatesthe piezoelectric element by flowing current to the piezoelectricelement, wherein an inductor and a resistor are insertion connected inparallel respectively to the piezoelectric oscillator of thehigh-frequency piezoelectric oscillator, and resonance frequency of aparallel resonance circuit consisting of the inductor and the resistoris set to the vicinity of the oscillation frequency of thehigh-frequency piezoelectric oscillator thereby to increase negativeresistance applied to a series arm of the piezoelectric element andsuppress unwanted oscillation due to the inductor.

[0018] According to a second aspect of the present invention, there isprovided a high-frequency piezoelectric oscillator including apiezoelectric oscillator having a piezoelectric element that is excitedin a predetermined frequency, and an oscillation amplifier thatoscillates the piezoelectric element by flowing current to thepiezoelectric element, wherein a circuit having an inductor and avariable capacitance diode connected in series and a resistor areinsertion connected in parallel respectively to the piezoelectricoscillator of the high-frequency piezoelectric oscillator, resonancefrequency of a parallel resonance circuit consisting of the inductor andthe resistor is set to the vicinity of the oscillation frequency of thehigh-frequency piezoelectric oscillator, thereby to increase negativeresistance applied to a series arm of the piezoelectric element andexternally fine adjust the capacitance of the variable capacitance diodeso as to optimize oscillation and make it possible to control frequency.

[0019] According to a third aspect of the present invention, there isprovided a high-frequency piezoelectric oscillator including apiezoelectric oscillator having a piezoelectric element that is excitedin a predetermined frequency, and an oscillation amplifier thatoscillates the piezoelectric element by flowing current to thepiezoelectric element, wherein a first inductor and a resistor areconnected in parallel respectively to the piezoelectric oscillator ofthe high-frequency piezoelectric oscillator, the connection point isgrounded via a circuit having a second inductor and a variablecapacitance diode connected in series, and resonance frequency of aparallel resonance circuit consisting of the first inductor and theresistor is set to the vicinity of the resonance frequency of thehigh-frequency piezoelectric oscillator, thereby to increase negativeresistance applied to a series arm of the piezoelectric element andexternally fine adjust the capacitance of the variable capacitance diodeso as to optimize oscillation and make it possible to control frequency.

[0020] According to a fourth aspect of the present invention, there isprovided a high-frequency piezoelectric oscillator according to any oneof the first to third aspects, wherein the following relationships arefulfilled: $\begin{matrix}{{{{R_{1} + R_{L}} = {{{{0 \cdot \omega}\quad L_{1}} + \frac{1}{\omega \cdot C_{1}} + X_{L}} = 0}}{when}{X_{0} = {{\frac{1}{\omega \quad C_{0}} \times \frac{1}{\left( {1 - \frac{\omega_{0}^{2}}{\omega^{2}}} \right)}} = {\frac{1}{\omega \quad C_{0}} \times \frac{1}{\left( {\frac{\omega_{0}^{2}}{\omega^{2}} - 1} \right)}}}}{z_{0} = {\frac{R_{0}X_{0}^{2}}{R_{0}^{2} + X_{0}^{2}} + {j\frac{X_{0}R_{0}^{2}}{R_{0}^{2} + X_{0}^{2}}}}}{r_{\alpha} = \frac{R_{0}X_{0}^{2}}{R_{0}^{2} + X_{0}^{2}}},\quad {{\ldots \quad X_{\alpha}} = \frac{X_{0}R_{0}^{2}}{R_{0}^{2} + X_{0}^{2}}},{Z_{L} = \frac{{{- r_{\alpha}}R_{c}} + {X_{\alpha}X_{c}} - {j\left( {{X_{\alpha}R_{c}} + {X_{c}r_{\alpha}}} \right)}}{r_{\alpha} - R_{c} + {j\left( {X_{\alpha} - X_{c}} \right)}}},\quad \ldots}{{A = {r_{\alpha} - R_{c}}},\quad {{\ldots \quad B} = {X_{\alpha} - X_{c}}},\quad {{\ldots \quad C} = {R_{c}^{2} + X_{c}^{2}}},\quad {{\ldots \quad D} = {{r_{\alpha}^{2} + {X_{\alpha}^{2}R_{L}}} = \frac{{r_{\alpha} \times C} - {R_{c} \times D}}{A^{2} + B^{2}}}},\quad {{\ldots \quad X_{L}} = \frac{{X_{c} \times D} - {X_{\alpha} \times C}}{A^{2} + B^{2}}},}} & (I)\end{matrix}$

[0021] where −Rc represents the negative resistance, Cc representscircuit capacitance, C0 represents interelectrode capacitance of thepiezoelectric oscillator, X0 represents reactance of a parallel circuitof the inductor L0, R0 represents resistance of the resistor, −Xcrepresents circuit capacitance of the circuit, rα represents parallelconnection resistance of the X0 and R0, Xα represents reactance, RLrepresents negative resistance of the series arm of the oscillator, XLrepresents reactance, and (I) represents an oscillation condition.

[0022] According to a fifth aspect of the present invention, there isprovided a high-frequency piezoelectric oscillator according to thefirst aspect wherein

[0023] ω₁<ω₂<ω₂ (Exp. 1) is fulfilled, when

[0024] ω_(T) represents unwanted resonance non-angular frequency, C_(o)represents interelectrode capacitance of the oscillator, Rc representsan absolute value of negative resistance of an additional resistor andan oscillation circuit that are connected in parallel to the C_(o),L_(o) represents an additional inductor that is connected in parallel tothe C_(o), and ω_(o) represents parallel resonance angular frequency ofthe C_(o) and L_(o), where (Exp. 2) to (Exp. 4) are fulfilled$\begin{matrix}{\begin{matrix}{{{\ldots \quad \omega_{1}} = \sqrt{\omega_{0}^{2} + \frac{K - \sqrt{K\left( {K + {4\omega_{0}^{2}}} \right)}}{2}}},\quad {\ldots \quad \omega_{2}}} \\{{= \sqrt{\omega_{0}^{2} + \frac{K + \sqrt{K\left( {K + {4\omega_{0}^{2}}} \right)}}{2}}},\quad {\ldots \quad K}} \\{{= \frac{M}{C_{0}^{2}R_{0}^{2}}},\quad {{\ldots \quad M} = {\frac{R_{0}}{R_{c}} - 1}}}\end{matrix}\quad {{M > 0},{R_{0} > {R\quad c}}}} & \left( {{Exp}.\quad 2} \right) \\{{...\quad ._{\quad T}} =_{\cdot \quad 2^{\quad -} \cdot \quad 1}{= {\sqrt{\frac{K^{2}}{4._{0}^{2}} + K} = {\frac{\,^{.}0}{2\quad Q_{0}}\sqrt{M\left( {{4\quad Q_{0}} + M} \right)}}}}} & \left( {{Exp}.\quad 3} \right)\end{matrix}$

[0025] T: Unwanted resonance non-angular bandwidth $\begin{matrix}{{\ldots \quad Q} = {\frac{R_{0}}{{}_{\quad^{.}0}^{}{}_{}^{}} = {{{}_{\quad^{.}0}^{}{}_{}^{}}R_{0}\quad \ldots}}} & \left( {{Exp}.\quad 4} \right)\end{matrix}$

[0026] the (Exp. 1) represents unwanted resonance non-angular bandwidth,(Exp. 2) represents a condition for fulfilling the (Exp. 1), and (Exp.3) represents an unwanted band,

[0027] (Exp. 5) is fulfilled, where $\begin{matrix}\begin{matrix}{{\ldots \quad R_{L}} = {\frac{{r_{.} \times C} - {R_{c} \times D}}{A^{2} + B^{2}}\quad \ldots \quad X_{L}}} \\{= {{\frac{{X_{.} \times C} - {X_{c} \times D}}{A^{2} + B^{2}}.\quad \ldots}\quad r_{.}}} \\{{= \frac{R_{0}X_{0}^{2}}{R_{0}^{2} + X_{0}^{2}}},\quad {{\ldots \quad X_{.}} = \frac{X_{0}R_{0}^{2}}{R_{0}^{2} + X_{0}^{2}}},\quad {\ldots \quad X_{0}}} \\{{= \frac{1}{..{C_{0}\left( {\frac{._{0}^{2}}{.^{2}} - 1} \right)}}},\quad {{\ldots \quad X_{c}} = {\frac{1}{..C_{c}}\quad \ldots \quad A}}} \\{{= {r_{.} - R_{c}}},\quad {{\ldots \quad B} = {X_{.} - X_{c}}},\quad {\ldots \quad C}} \\{{= {R_{c}^{2} + X_{c}^{2}}},\quad {{\ldots \quad D} = {r_{.}^{2} + X_{.}^{2}}}}\end{matrix} & \left( {{Exp}.\quad 5} \right)\end{matrix}$

[0028] Q represents parallel resonance angular frequency which is aratio of a real number to reactance shown by the ω_(o) in the (Exp. 4),RL represents the negative resistance for oscillating the series armconsisting of L1/C1/R0 of the oscillator, XL represents reactance, Ccrepresents circuit capacitance of the oscillation circuit, and ωrepresents oscillation angular frequency, and

[0029] (Exp. 5) represents negative resistance and load capacitance foroscillating a series arm consisting of L1/C1/R0 of the oscillator.

[0030] According to a sixth aspect of the present invention, there isprovided a high-frequency piezoelectric oscillator according to any oneof the first, second, third and fourth aspects, wherein the resistancewithin a range according to the fifth aspect is organized within aninductor, and the inductor having the inductor and the resistorintegrated together is connected in parallel to the interelectrodecapacitance C_(o) of the oscillator.

BRIEF DESCRIPTION OF THE DRAWINGS

[0031]FIG. 1 is a configuration diagram of a first high-frequencypiezoelectric oscillator according to the present invention;

[0032]FIG. 2 is a configuration diagram of an equivalent circuit 1 ofthe first high-frequency piezoelectric oscillator according to thepresent invention;

[0033]FIG. 3 is a configuration diagram of an equivalent circuit 2 ofthe first high-frequency piezoelectric oscillator according to thepresent invention;

[0034]FIG. 4 is a configuration diagram of an equivalent circuit 3 ofthe first high-frequency piezoelectric oscillator according to thepresent invention;

[0035]FIG. 5 is a configuration diagram of an equivalent circuit 4 ofthe first high-frequency piezoelectric oscillator according to thepresent invention;

[0036]FIG. 6 illustrates a relationship between load resistance RL,circuit negative resistance Rc, oscillator parallel capacitance, andparallel additional resistance R0 to an inductance L0 according to thepresent invention;

[0037]FIG. 7 illustrates a relationship between the parallel additionalresistance R0 and the load resistance RL connected to a series armaccording to the present invention;

[0038]FIG. 8 illustrates a relationship between load capacitance CL andfrequency;

[0039]FIG. 9 is a configuration diagram of an equivalent circuit thatshows unwanted oscillation of the first high-frequency piezoelectricoscillator according to the present invention;

[0040]FIG. 10 illustrates an unwanted oscillation region of the firsthigh-frequency piezoelectric oscillator according to the presentinvention;

[0041]FIG. 11 is a graph of unwanted resonance frequency according tothe present invention;

[0042]FIG. 12 illustrates a relationship between unwanted resonancefrequency and circuit capacitance;

[0043]FIG. 13 is a circuit diagram of a high-frequency piezoelectricoscillator according to the first embodiment of the present invention;

[0044]FIG. 14 is a waveform diagram of an oscillation circuit accordingto the present invention;

[0045]FIG. 15 illustrates power supply variation characteristics of theoscillation circuit according to the present invention;

[0046]FIG. 16 illustrates a result of a simulation carried out using theoscillation circuit according to the present invention;

[0047]FIG. 17 is a circuit diagram of a high-frequency piezoelectricoscillator according to the second embodiment of the present invention;

[0048]FIG. 18 is a circuit diagram of a high-frequency piezoelectricoscillator according to the third embodiment of the present invention;

[0049]FIG. 19 illustrates a relationship between additional resistanceR0, load resistance RL, and unwanted resonance frequency whenoscillation frequency is 622 MHz according to the present invention;

[0050]FIG. 20 illustrates a relationship between Q, negative resistanceRL, and unwanted resonance bandwidth, where the Q changes by changingthe additional resistance R0 in the parallel resonance of C0/L0/R0 whenthe parallel resonance frequency f0=600 MHz, according to the presentinvention;

[0051]FIG. 21 illustrates a relationship between negative resistance ofa series arm and unwanted resonance bandwidth when the additionalresistance is fixed to R0=200Ω and when the negative resistance of thecircuit is variable;

[0052]FIG. 22 illustrates one example of a conventional Colpitts typeoscillator;

[0053]FIG. 23 illustrates another example of a conventional Colpittstype oscillator;

[0054]FIG. 24 illustrates an equivalent circuit model of a conventionalcircuit;

[0055]FIG. 25 illustrates a result of carrying out a simulation aboutcharacteristics of negative resistance Rc and circuit capacitance Cc ofa representative Colpitts oscillation circuit;

[0056]FIG. 26 illustrates X0 that represents reactance of a parallelresonance circuit of the parallel capacitance C0 and the inductor L0 ofthe oscillator of the equivalent circuit shown in FIG. 24;

[0057]FIG. 27 illustrates X0 that represents reactance of a parallelresonance circuit of the parallel capacitance C0 and the inductor L0 ofthe oscillator of the equivalent circuit shown in FIG. 24;

[0058]FIG. 28 illustrates characteristics of series arm load resistanceRL based on the diagram shown in FIG. 27;

[0059]FIG. 29 illustrates a relationship between series arm loadcapacitance and frequency based on the diagram shown in FIG. 27;

[0060]FIG. 30 illustrates an unwanted resonance loop;

[0061]FIG. 31 illustrates unwanted resonance frequency; and

[0062]FIG. 32 illustrates a relationship between unwanted resonancefrequency and circuit capacitance.

DETAILED DESCRIPTIONS

[0063] High-frequency piezoelectric oscillator according to embodimentsof the present invention will be explained in detail below withreference to the accompanying drawings. Unless specified otherwise, thescope of the present invention is not limited to constituent elements,kinds, combinations, shapes, and relative arrangements described in theembodiments. These show only examples.

[0064]FIG. 1 is a configuration diagram of a first high-frequencypiezoelectric oscillator according to the present invention. In thishigh-frequency piezoelectric oscillator, a series circuit of capacitorsC1 and C2 as a part of a load capacitance are connected between a baseof a transistor TR1 and the ground. The connection point of thecapacitors C1 and C2 is connected to an emitter of a transistor TR21,and is grounded via a resistor R1. A base bias circuit consisting of aresistor RB1 and a resistor RB2 is connected to the base of thetransistor TR1. A parallel circuit of a piezoelectric vibrator (X′tal),an inductor L0, and a resistor R0 is connected to a capacitor C3, andthe parallel circuit is connected to the base of the transistor TR1, andthe capacitor is connected to the ground. A collector of the transistorTR1 and a power supply line (Vcc) are connected together.

[0065]FIG. 2 is a configuration diagram of an equivalent circuit 1 ofthe first high-frequency piezoelectric oscillator, shown in FIG. 1,according to the present invention. C0 represents interelectrodecapacitance of the piezoelectric vibrator (X′tal), L1 represents aninductor, C1 represents capacitance, R1 represents resistance, −Rcrepresents negative resistance of an oscillation circuit, and Ccrepresents circuit capacitance. FIG. 3 is a configuration diagram of anequivalent circuit 2, where X0 represents reactance of a parallelcircuit of the interelectrode capacitance C0 of the piezoelectricvibrator (X′tal) and an inductor L0, and −Xc represents circuitcapacitance of the circuit. In this equivalent circuit 2, the reactanceX0 and a resistance R0 is connected in parallel. FIG. 4 is aconfiguration diagram of an equivalent circuit 3, where the parallelcircuit of the reactance X0 and the resistance R0 in FIG. 3 is convertedto a series circuit of a resistance rα and reactance Xα. In this FIG. 3,−Rc represents negative resistance of the oscillation circuit, and Xcrepresents circuit capacitance. FIG. 5 shows an equivalent circuitconsisting of the negative resistance RL and XL that are converted fromthe series circuit connected to the piezoelectric vibrator (X′tal)(hereinafter, the series circuit connected to the piezoelectric vibratoris referred to as “series arm”). Exp. (8) shows an oscillation conditionof the equivalent circuit shown in FIG. 3. $\begin{matrix}\begin{matrix}{{{{\ldots \quad R_{1}} + R_{L}} = 0}\quad} \\{{{{\cdot \omega}\quad L_{1}} + \frac{1}{\omega \cdot C_{1}} + X_{L}} = 0}\end{matrix} & (8)\end{matrix}$

[0066] The reactance X0 shown in FIG. 3 is obtained, and Exp. (9) isobtained. $\begin{matrix}\begin{matrix}{{{j\quad X_{0}} = \frac{\frac{L_{0}}{C_{0}}}{{j\quad \omega \quad L_{0}} + \frac{1}{j\quad \omega \quad C_{0}}}},\quad {\ldots \quad \omega_{0}^{2}}} \\{{= {{\frac{1}{L_{0}C_{0}}\quad \ldots \quad \omega_{0}} = {\frac{1}{\sqrt{L_{0}C_{0}}}\quad \ldots}}}\quad} \\{= {\frac{L_{0}}{C_{0}} \times \frac{1}{j\quad \omega \quad {L_{0}\left( {1 - \frac{1}{\omega^{2}\quad C_{0}L_{0}}} \right)}}}} \\{= {\frac{1}{j\quad \omega \quad C_{0}} \times \frac{1}{\left( {1 - \frac{1}{\omega^{2}\quad C_{0}L_{0}}} \right)}}} \\{= {{- j}\frac{1}{\omega \quad C_{0}} \times \frac{1}{\left( {1 - \frac{1}{\omega^{2}\quad C_{0}L_{0}}} \right)}\quad \ldots \quad X_{0}}} \\{= {{{- \frac{1}{\omega \quad C_{0}}} \times \frac{1}{\left( {1 - \frac{\omega_{0}^{2}}{\omega^{2}\quad}} \right)}} = {\frac{1}{\omega \quad C_{0}} \times \frac{1}{\left( {\frac{\omega_{0}^{2}}{\omega^{2}\quad} - 1} \right)}}}}\end{matrix} & (9)\end{matrix}$

[0067] The resistance rα and the reactance Xα shown in FIG. 4 areobtained, and Exp. (10) is obtained. The resistance RL and the reactanceXL shown in FIG. 5 are obtained, and Exp. (11) is obtained.$\begin{matrix}\begin{matrix}{{\ldots \quad z_{0}} = {\frac{j\quad X_{0} \times R_{0}}{R_{0} + {j\quad X_{0}}} = \frac{j\quad X_{0} \times {R_{0}\left( {R_{0} - {j\quad X_{0}}} \right)}}{R_{0}^{2} + X_{0}^{2}}}} \\{= {\frac{X_{0} \times {R_{0}\left( {X_{0} + {j\quad R_{0}}} \right)}}{R_{0}^{2} + X_{0}^{2}} = {\frac{R_{0}X_{0}^{2}}{R_{0}^{2} + X_{0}^{2}} + {j\frac{X_{0}R_{0}^{2}}{R_{0}^{2} + X_{0}^{2}}\quad \ldots \quad r_{\alpha}}}}} \\{{= \frac{R_{0}X_{0}^{2}}{R_{0}^{2} + X_{0}^{2}}},\quad {{\ldots \quad X_{\alpha}} = \frac{X_{0}R_{0}^{2}}{R_{0}^{2} + X_{0}^{2}}}}\end{matrix} & (10) \\\begin{matrix}{{{\ldots \quad Z_{L}} = {\frac{\left( {r_{\alpha} + {j\quad X_{\alpha}}} \right)\left( {{- R_{c}} - {j\quad X_{c}}} \right)}{r_{\alpha} + {j\quad X_{\alpha}} - R_{c} - {j\quad X_{c}}}\quad \ldots}}\quad} \\{{= \frac{{{- r_{\alpha}}R_{c}} + {X_{\alpha}X_{c}} - {j\left( {{X_{\alpha}R_{c}} + {X_{c}r_{\alpha}}} \right)}}{r_{\alpha} - R_{c} + {j\quad \left( {X_{\alpha} - X_{c}} \right)}}},\quad {\ldots \quad A}} \\{{= {r_{\alpha} - R_{c}}},\quad {{\ldots \quad B} = {X_{\alpha} - X_{c}}},\quad {\ldots \quad C}} \\{{= {R_{c}^{2} + X_{c}^{2}}},\quad {{\ldots \quad D} = {r_{\alpha}^{2} + {X_{\alpha}^{2}\quad \ldots \quad R_{L}}}}} \\{{= \frac{{r_{\alpha} \times C} - {R_{c} \times D}}{A^{2} + B^{2}}},\quad {{\ldots \quad X_{L}} = \frac{{X_{c} \times D} - {X_{\alpha} \times C}}{A^{2} + B^{2}}}}\end{matrix} & (11)\end{matrix}$

[0068]FIG. 6 illustrates a relationship between the resistance R0 andthe load resistance RL, and a relationship between the resistance R0 andthe capacitance CL obtained from the Exps. (10) and (11). The left sideof the axis of an ordinate represents the load resistance RL, the rightside of the axis of an ordinate represents the capacitance CL, and theaxis of an abscissa represents the parallel resistance R0. From FIG. 6,it is clear from the variation of the load resistance RL that connectsto the series arm, there is an optimum value for the parallel resistanceR0. In other words, it is clear that the load resistance RL is stablewhen the parallel resistance R0 is approximately 200Ω. The parallelresonance frequency of the L0 and C0 is 600 MHz, the oscillationfrequency is 620 MHz, and C0=3 pF.

[0069]FIG. 7 illustrates a relationship between the load resistance RLconnected to the series arm and the oscillation frequency depending onthe parallel resistance R0 (200Ω, 300Ω, and 600Ω). The ordinaterepresents the load resistance RL, and the abscissa representsfrequency. From FIG. 7, it is clear that when the parallel resistance R0increases, the load resistance RL of the series arm. The parallelresonance frequency of the L0 and C0 is 600 MHz, C0=3 pF, and Ce=30 pF.

[0070]FIG. 8 illustrates a relationship between the load capacitance CLand frequency. The ordinate represents the load capacitance CL, and theabscissa represents frequency. From FIG. 8, it is clear that the circuitcapacitance CL is capacitive at 580 MHz or above when the parallelresonance frequency f0 defined by the L0 and Co is 600 MHz.

[0071]FIG. 9 is an equivalent circuit of the present invention shown inFIG. 1 under the condition of an unwanted oscillation state. Exp. (12)represents a condition that the circuit does not oscillate. Exp. (13)represents a condition that the circuit can oscillate. Exp. (14)represents an oscillation frequency condition.

r _(α) −R _(c)>0  (12)

r _(α) −R _(c)<0  (13)

X _(α) −X _(c)=0  (14)

[0072]FIG. 10 illustrates an unwanted oscillation region of the circuit,shown in FIG. 1, according to the present invention. The ordinaterepresents rα−Rc, and the abscissa represents frequency. From FIG. 10,it is clear that in the frequency region from about 480 MHz to 750 MHz,the series resistance rα that occurs based on the resistance R0 parallelconnected to the oscillator becomes larger than the negative resistanceRc that occurs from the circuit. As this state fulfills the Exp. (12),this region becomes an oscillation impossible region 3. As is clear fromthe characteristics curves 5 and 6, this region is constant regardlessof R0. In other regions 1 and 2, oscillation is possible. However, Qrdue to the inductor L0 and the resistance R0 becomes as shown in FIG.10.

[0073]FIG. 11 represents a relationship between unwanted resonancefrequency ft and resistance Xα−Xc when Cc=1, 3, 5, 10, 30, and 100 pFrespectively in a condition that C0=3 pF, the parallel resonancefrequency is f0=600 MHz, and the circuit negative resistance Rc=−100Ω.The frequency when Xα−Xc=0 on each characteristic curve is unwantedresonance frequency. From FIG. 11, it is clear that the unwantedresonance frequency is present in the frequency lower than 600 MHz.However, in the frequency of 480 MHz or above, the oscillator cannotoscillate as is clear from FIG. 10. In the frequency not higher than 400MHz, the negative resistance of the Colpitts oscillation circuit shownin FIG. 25 does not occur, and therefore, the oscillator cannotoscillate.

[0074]FIG. 12 illustrates a relationship between unwanted resonancefrequency and circuit capacitance. The ordinate represents unwantedresonance frequency, and the abscissa represents circuit capacitance.From FIG. 12, it is clear that when Cc is 5 pF or above, low frequencyunwanted resonance occurs in the frequency 400 MHz or below, and highfrequency unwanted resonance occurs in the frequency 580 MHz or above.

[0075] As explained above, according to the circuit of the presentinvention shown in FIG. 1, it is made clear by the simulation that theincrease in the negative resistance and unwanted oscillation can beprevented, by connecting the inductor L0 to the parallel capacitance C0of the oscillator and by connecting proper resistance R0 in parallel.

[0076] A frequency band in which unwanted resonance does not occur isobtained next.

[0077] This operation is the same as obtaining a range in which anabsolute value |R_(c)| of the negative resistance of the circuit issmaller than series resistance r_(α).

[0078] Conditions for not generating unwanted resonance are obtainedfrom the Exp. (10), the Exp. (4), and the Exp. (12). $\begin{matrix}{{{\ldots \quad r_{\alpha}} = \frac{R_{0} \times X_{0}^{2}}{R_{0}^{2} + X_{0}^{2}}},{{\ldots \quad X_{0}} = {{{\frac{1}{\omega \quad {C_{0}\left( {\frac{\omega_{0}^{2}}{\omega^{2}} - 1} \right)}}\quad \ldots \quad r_{\alpha}} - R_{c}} > 0}}} & (15) \\\left. {{{\ldots \quad \frac{R_{0}X_{0}^{2}}{R_{0}^{2} + X_{0}^{2}}} - R_{c}} > {0\quad \ldots}}\rightarrow{{\ldots \quad \frac{1}{X_{0}^{2}}} < {\frac{1}{R_{0}^{2}}\left( {\frac{R_{0}}{R_{c}} - 1} \right)}} \right. & \quad \\{\left. {{\ldots \quad \omega^{2}{C_{0}^{2}\left( {\frac{\omega_{0}^{2}}{\omega^{2}} - 1} \right)}^{2}} < {\frac{1}{R_{0}^{2}}\left( {\frac{R_{0}}{R_{c}} - 1} \right)\quad \ldots}}\rightarrow{{\ldots \quad {\omega^{2}\left( {\frac{\omega_{0}^{2}}{\omega^{2}} - 1} \right)}^{2}} < {\frac{1}{C_{0}^{2}R_{0}^{2}}\left( {\frac{R_{0}}{R_{c}} - 1} \right)}} \right.,} & \quad \\{{{\ldots \quad \Theta \quad K} = \frac{M}{C_{0}^{2}R_{0}^{2}}},{{\ldots \quad M} = \left( {\frac{R_{0}}{R_{c}} - 1} \right)}} & \quad \\\left. {{\ldots \quad {\omega^{2}\left( {\frac{\omega_{0}^{2}}{\omega^{2}} - 1} \right)}^{2}} < {K\quad \ldots}}\rightarrow\left. {{\frac{\omega_{0}^{4}}{\omega^{2}} - {2\quad \omega_{0}^{2}} + \omega^{2}} < {K\quad \ldots}}\rightarrow{{{\ldots \quad \omega^{4}} - {\left( {{2\quad \omega_{0}^{2}} + K} \right)\omega^{2}} + \omega_{0}^{4}} < 0} \right. \right. & (16) \\{{.{\int\left( \omega^{2} \right)}} = {\omega^{4} - {\left( {{2\quad \omega_{0}^{2}} + K} \right)\omega^{2}} + \omega_{0}^{4}}} & (17)\end{matrix}$

[0079] From the Exp. (17), a root is obtained by setting f(ω²)=0.$\begin{matrix}{{\ldots \quad \omega^{2}} = {{\omega_{0}^{2} + {\frac{K}{2} \pm \frac{\sqrt{K\left( {K + {4\omega_{0}^{2}}} \right)}}{2}}} = {\omega_{0}^{2} + \frac{K \pm \sqrt{K\left( {K + {4\omega_{0}^{2}}} \right)}}{2}}}} & (18) \\{\begin{matrix}{{{\ldots \quad \omega_{1}^{2}} = {\omega_{0}^{2} + \frac{K - \sqrt{K\left( {K + {4\omega_{0}^{2}}} \right)}}{2}}},\quad {\ldots \quad \omega_{1}}} \\{= \sqrt{\omega_{0}^{2} + \frac{K - \sqrt{K\left( {K + {4\omega_{0}^{2}}} \right)}}{2}}}\end{matrix}\quad} & (19) \\{\begin{matrix}{{{\ldots \quad \omega_{2}^{2}} = {\omega_{0}^{2} + \frac{K + \sqrt{K\left( {K + {4\omega_{0}^{2}}} \right)}}{2}}},\quad {\ldots \quad \omega_{2}}} \\{= \sqrt{\omega_{0}^{2} + \frac{K + \sqrt{K\left( {K + {4\omega_{0}^{2}}} \right)}}{2}}}\end{matrix}\quad} & (20)\end{matrix}$

[0080] Exp. (21) is obtained when the unwanted resonance non-angularbandwidth is ω_(T).

ω₁<ω_(T)<ω₂  (21)

[0081] The bandwidth is obtained. $\begin{matrix}{{{{\ldots \quad \omega_{2}^{2}} - \omega_{1}^{2}} = {{\left( {\omega_{2} - \omega_{1}} \right)\left( {\omega_{2} + \omega_{1}} \right)} = \sqrt{K\left( {K + {4\quad \omega_{0}^{2}}} \right)}}},{{{\ldots \quad \omega_{2}} + \omega_{1}} = {2\quad \omega_{0}}}} & (22)\end{matrix}$

[0082] From the Exp. (22), the bandwidth is set to ΔωT, and Exp. (23) isobtained. $\begin{matrix}{{\ldots \quad \Delta \quad \omega_{T}} = {{\omega_{2} - \omega_{1}} = {\frac{\sqrt{K\left( {K + {4\quad \omega_{0}^{2}}} \right)}}{2\quad \omega_{0}} = \sqrt{\frac{K^{2}}{4\quad \omega_{0}^{2}} + K}}}} & (23)\end{matrix}$

[0083] Q when the parallel resonance frequency of C₀/L₀/R₀ is ω₀ isobtained from Exp. (24). $\begin{matrix}{Q = {\frac{R_{0}}{\omega_{0}L_{0}} = {\omega_{0}C_{0}R_{0}}}} & (24)\end{matrix}$

[0084] The Exp. (24) is substituted into Exp. (15) to obtain Exp. (25).$\begin{matrix}{{{\ldots \quad K} = {\frac{M}{C_{0}^{2}R_{0}^{2}} = \frac{\omega_{0}^{2}M}{Q^{2}}}},{{\ldots \quad M} = {\frac{R_{0}}{R_{c}} - 1}}} & (25) \\{{\ldots \quad \left( {\Delta \quad \omega_{T}} \right)^{2}} = {{{\frac{1}{4\quad \omega_{0}^{2}} \times \frac{\omega_{0}^{4}}{Q^{4}}M^{2}} + {\frac{\omega_{0}^{2}}{Q^{2}}{M.}}} = {\frac{\omega_{0}^{2}}{Q^{2}}M\left\{ {1 + {\frac{1}{4\quad \omega_{0}^{2}} \times \frac{\omega_{0}^{2}}{Q^{2}}M}} \right\}}}} & \quad \\{\quad {\ldots \quad = {{\frac{\omega_{0}^{2}}{Q^{2}}M\left\{ {1 + \frac{1}{4} + {\frac{1}{Q^{2}}M}} \right\}} = {{\frac{\omega_{0}^{2}}{Q^{2}}M\frac{{4Q^{2}} + M}{4Q^{2}}} = {\frac{\omega_{0}^{2}}{4Q^{4}}M\left\{ {Q^{2} + M} \right\}}}}}} & \quad \\{{\ldots \quad \Delta \quad \omega_{T}} = {\frac{\omega_{0}}{2Q^{2}}\sqrt{M\left( {{4Q^{2}} + M} \right)}}} & (26)\end{matrix}$

[0085] Exp. (26) shows the unwanted resonance non-angular bandwidthusing Q.

[0086]FIG. 13 is a circuit diagram of a high-frequency piezoelectricoscillator according to the first embodiment of the present invention.This high-frequency piezoelectric oscillator comprises an oscillationcircuit 20 and an output circuit 30. The output circuit 30 is not a mainportion of the present invention, and therefore, its explanation will beomitted. Only the oscillation circuit 20 will be explained. CapacitorsC1 and C2 that become a part of the load capacitance are connectedbetween the base of the transistor TR1 and the ground. The connectionpoint of the capacitors C1 and C2 is connected to an emitter of thetransistor TR1, and is grounded via the emitter resistance R1. A basebias circuit consisting of the resistor RB1 and the resistor RB2 isconnected to the base of the transistor TR1. The piezoelectric vibrator(X′tal), the inductor L0, and the resistor R0 are connected in parallel,and the parallel circuit is connected between the base of the transistorTR1 and a capacitor C3. The capacitor C3 is grounded. Further, thecollector of the transistor TR1 and the power supply line (Vcc) areconnected.

[0087] In the present invention, the TR1 is MT4S101T, C1=5 pF, C2=8 pF,C3=100 pF, R1=180Ω, RB1=10 KΩ, and RB2=22 KΩ. As parameters of thepiezoelectric vibrator (X′tal), the interelectrode capacitance of theoscillator is C0=3.5 pF, and the capacitance ratio is C0/C1=451. Figure.rate merit that represents a good level of the oscillator is M=1.39 (nooscillation occurs in the inductive region when M<2). The parallelconnection inductor L0=22 nH, and Q=20. Based on Q=20, resistance thatfloats in the inductor is about 1500Ω, and the parallel connectionresistance is R0=470Ω. From this, the inductor parallel resistancebecomes 1500Ω//470Ω=360Ω, and the resonance frequency of the oscillatorX′tal becomes 600 MHz.

[0088]FIG. 14 is a waveform diagram of the oscillation circuit 20according to the present invention. From FIG. 14, it is clear that thefrequency is stable in about 600 MHz, and the waveform has smalldistortion.

[0089]FIG. 15 illustrates power supply variation characteristics of theoscillation circuit 20 according to the present invention. From FIG. 15,it is confirmed that no abnormal oscillation occurs due to variation inthe power supply and frequency. It is also confirmed that theoscillation is from the oscillator and is not unwanted oscillation, fromthe stable level of the oscillation (±2 ppm @ ±5% VCC or below).Therefore, it is clear from the result that the oscillation is theoscillator oscillation.

[0090]FIG. 16 illustrates a result of a simulation carried out using theoscillation circuit 20 when the parallel capacitance of the oscillatoris C0=3.5 pF, the parallel connection inductor is L0=22 nH, and theparallel connection resistance is R0=470Ω. From this result, it is clearthat when the frequency is 620 MHz, the conversion capacitance is Cα=0.5pF, the conversion resistance rα=240Ω, and the negative resistance isRL=−137Ω. In other words, it is clear that the present invention is avery effective method to solve the problem of the increase in theinterelectrode capacitance of the oscillator and the reduction in the“Figure of Merit” when the oscillator is in high frequency.

[0091]FIG. 17 is a circuit diagram of a high-frequency piezoelectricoscillator according to the second embodiment of the present invention.As like constituent elements are designated with like referencenumerals, a redundant explanation will be omitted. The configurationshown in FIG. 17 is different from that shown in FIG. 1 in that avariable capacitance diode D1 is inserted in series into the inductorL0, and peripheral circuits R2, R3, and C4 are added. With thisarrangement, a voltage is applied to a V.CON terminal to make thecapacitance of the inductor L0 variable, thereby to optimize theoscillation and make it possible to control frequency.

[0092]FIG. 18 is a circuit diagram of a high-frequency piezoelectricoscillator according to the third embodiment of the present invention.As like constituent elements are designated with like referencenumerals, a redundant explanation will be omitted. The configurationshown in FIG. 18 is different from that shown in FIG. 1 in that thevariable capacitance diode D1 and an inductor L1 is inserted in seriesinto the capacitor C3, and the peripheral circuits R3 and C4 are added.With this arrangement, a voltage is applied to the V.CON terminal tomake the capacitance of the inductor L0 variable, thereby to optimizethe oscillation and make it possible to control frequency.

[0093] While the present invention is explained above using theoscillation circuit having the fundamental frequency of the oscillatoras the oscillation frequency, the present invention is not limited tothis arrangement. It is also possible to apply the invention to anoscillation circuit having overtone frequency of third order, fifthorder, a seventh order, or a higher order of the oscillator asoscillation frequency.

[0094]FIG. 19 illustrates a relationship with the additional resistanceR0, the load resistance RL, and the unwanted resonance frequency whenthe oscillation frequency is 622 MHz.

[0095] The negative resistance of the circuit is −160Ω, and theresistance R0 to the parallel capacitance C0 of the oscillator exceedsthe absolute value of this negative resistance. Therefore, an unwantedresonance non-angular bandwidth occurs. A maximum bandwidth of about 170MHz is obtained at about 300Ω. The negative resistance of a series armof the piezoelectric vibrator consisting of the C1/L1/R1 decreases whenthe circuit capacitance becomes smaller, and has a maximum value whenthe R0 is between 200Ω and 300Ω. This value becomes about −500Ω which isabout three times the negative resistance −160Ω of the circuit, whenCc=50 pF.

[0096]FIG. 20 illustrates a relationship with Q at the parallelresonance of C0/L0/R0, the load resistance RL, and the unwantedresonance bandwidth, where the Q changes by changing the resistance R0.The parallel resonance frequency f0=600 MHz.

[0097] The negative resistance of the series arm shows a maximum valuewhen Q is between 2 and 3, and the unwanted resonance bandwidth shows amaximum value when Q is between 3 and 4. The bandwidth naturally becomessmaller when Q becomes larger.

[0098]FIG. 21 illustrates a relationship between the negative resistanceof the series arm and the unwanted resonance bandwidth when theadditional resistance is fixed to R0=200Ω and when the negativeresistance of the circuit is variable.

[0099] The negative resistance of the series arm falls rapidly and theunwanted resonance bandwidth becomes larger when the negative resistanceof the circuit becomes smaller. Particularly, the unwanted resonancebandwidth spreads large to the high frequency side.

[0100] As explained above, the negative resistance of the series arm ofthe oscillator can be made larger when the inductor and the resistor ofproper resistance are added to the parallel capacitance of theoscillator. At the same time, unwanted resonance can be suppressed byadding the inductor. When the piezoelectric vibrator is used for theoscillator, the electrode that excites the vibrator cannot be removedfrom the vibrator. The vibrator becomes thinner when the frequencybecomes higher. Therefore, the interelectrode capacitance increases.This is a crucial problem of the piezoelectric vibrator. To overcome theproblem, the interelectrode capacitance (i.e., parallel capacitance) ofthe vibrator can be cancelled or bad influence can be minimized byadding the resistor of proper resistance in the present invention. Inother words, it is anticipated that the future piezoelectric oscillatorcan be adapted to higher frequency. As a result, the invention cangreatly contribute to the device or system that uses the piezoelectricvibrator.

[0101] As explained above, according to the first aspect of the presentinvention, a resistor and an inductor, those values are properrespectively, are connected in parallel to the piezoelectric vibrator.Therefore, the interelectrode capacitance due to the high-frequencypiezoelectric oscillation can be decreased, and oscillation due tounwanted resonance can be suppressed. Consequently, high stability canbe obtained.

[0102] According to the second aspect of the present invention, avariable capacitance diode is connected in series to the inductor.Therefore, the capacitance of the inductor can be made variable byexternally applying a voltage. Consequently, the oscillation can beoptimized, and frequency can be controlled.

[0103] According to the third aspect of the present invention, avariable capacitance diode is connected in series to a parallelresonance circuit. Therefore, the capacitance of the inductor can bemade variable by externally applying a voltage. Consequently, theoscillation can be optimized, and frequency can be controlled.

[0104] According to the fourth aspect of the present invention, a properequivalent circuit can accurately determine proper additional resistanceand inductance based on oscillation frequency.

[0105] According to the fifth and sixth aspects of the presentinvention, an inductor and a resistor of proper resistance are added tothe parallel capacitance of the oscillator. Therefore, the negativeresistance of the series arm of the oscillator can be increased, andunwanted resonance due to the addition of the inductor can berestricted.

What is claimed is:
 1. A high-frequency piezoelectric oscillatorincluding a piezoelectric vibrator having a piezoelectric element thatis excited in a predetermined frequency, and an oscillation amplifierthat oscillates the piezoelectric element by flowing current to thepiezoelectric element, wherein an inductor and a resistor are insertionconnected in parallel respectively to the piezoelectric vibrator of thehigh-frequency piezoelectric oscillator, and resonance frequency of aparallel resonance circuit consisting of the inductor and the resistoris set to the vicinity of the oscillation frequency of thehigh-frequency piezoelectric oscillator thereby to increase negativeresistance applied to a series arm of the piezoelectric element andsuppress unwanted oscillation due to the inductor.
 2. A high-frequencypiezoelectric oscillator including a piezoelectric oscillator having apiezoelectric vibrator that is excited in a predetermined frequency, andan oscillation amplifier that oscillates the piezoelectric vibrator byflowing current to a piezoelectric element, wherein a circuit having aninductor and a variable capacitance diode connected in series and aresistor are insertion connected in parallel respectively to thepiezoelectric vibrator of the high-frequency piezoelectric oscillator,resonance frequency of a parallel resonance circuit consisting of theinductor and the resistor is set to the vicinity of the oscillationfrequency of the high-frequency piezoelectric oscillator, thereby toincrease negative resistance applied to a series arm of thepiezoelectric element and externally fine adjust the capacitance of thevariable capacitance diode so as to optimize oscillation and make itpossible to control frequency.
 3. A high-frequency piezoelectricoscillator including a piezoelectric oscillator having a piezoelectricvibrator that is excited in a predetermined frequency, and anoscillation amplifier that oscillates the piezoelectric vibrator byflowing current to a piezoelectric element, wherein a first inductor anda resistor are connected in parallel respectively to the piezoelectricvibrator of the high-frequency piezoelectric oscillator, the connectionpoint is grounded via a circuit having a second inductor and a variablecapacitance diode connected in series, and resonance frequency of aparallel resonance circuit consisting of the first inductor and theresistor is set to the vicinity of the resonance frequency of thehigh-frequency piezoelectric oscillator, thereby to increase negativeresistance applied to a series arm of the piezoelectric element andexternally fine adjust the capacitance of the variable capacitance diodeso as to optimize oscillation and make it possible to control frequency.4. A high-frequency piezoelectric oscillator according to any one ofclaims 1 to 3, wherein the following relationships are fulfilled:$\begin{matrix}{{{{R_{1} + R_{L}} = {{{{0 \cdot \omega}\quad L_{1}} + \frac{1}{\omega \cdot C_{1}} + X_{L}} = {{0{when}X_{0}} = {{\frac{1}{\omega \quad C_{0}} \times \frac{1}{\left( {1 - \frac{\omega_{0}^{2}}{\omega^{2}}} \right)}} = {{\frac{1}{\omega \quad C_{0}} \times \frac{1}{\left( {\frac{\omega_{0}^{2}}{\omega^{2}} - 1} \right)}z_{0}} = {{\frac{R_{0}X_{0}^{2}}{R_{0}^{2} + X_{0}^{2}} + {j\frac{X_{0}R_{0}^{2}}{R_{0}^{2} + X_{0}^{2}}r_{\alpha}}} = \frac{R_{0}X_{0}^{2}}{R_{0}^{2} + X_{0}^{2}}}}}}}},{{\ldots \quad X_{\alpha}} = {{\frac{X_{0}R_{0}^{2}}{R_{0}^{2} + X_{0}^{2}}.Z_{L}} = \frac{{{- r_{\alpha}}R_{c}} + {X_{\alpha}X_{c}} - {j\left( {{X_{\alpha}R_{c}} + {X_{c}r_{\alpha}}} \right)}}{r_{\alpha} - R_{c} + {j\left( {X_{\alpha} - X_{c}} \right)}}}},\ldots}\quad {{A = {r_{\alpha} - R_{c}}},{{\ldots \quad B} = {X_{\alpha} - X_{c}}},{{\ldots \quad C} = {R_{c}^{2} + X_{c}^{2}}},{{\ldots \quad D} = {{r_{\alpha}^{2} + {X_{\alpha}^{2}R_{L}}} = \frac{{r_{\alpha} \times C} - {R_{c} \times D}}{A^{2} + B^{2}}}},{{\ldots \quad X_{L}} = \frac{{X_{c} \times D} - {X_{\alpha} \times C}}{A^{2} + B^{2}}},}} & (I)\end{matrix}$

where −Rc represents the negative resistance, Cc represents circuitcapacitance, C0 represents interelectrode capacitance of thepiezoelectric vibrator, X0 represents reactance of a parallel circuit ofthe inductor L0, R0 represents resistance of the resistor, −Xcrepresents circuit capacitance of the circuit, rα represents parallelconnection resistance of the X0 and R0, Xα represents reactance, RLrepresents negative resistance of the series arm of the oscillator, XLrepresents reactance, and (I) represents an oscillation condition.
 5. Ahigh-frequency piezoelectric oscillator according to claim 1, whereinω₁<ω_(T)<ω₂ (Exp. 1) is fulfilled, when ω_(T) represents unwantedresonance non-angular frequency, C_(o) represents interelectrodecapacitance of the vibrator, Rc represents an absolute value of negativeresistance of an additional resistor and an oscillation circuit that areconnected in parallel to the C_(o), L_(o) represents an inductor that isconnected in parallel to the C_(o), and ω₀ represents parallel resonanceangular frequency of the C_(o) and L_(o), where (Exp. 2) to (Exp. 4) isfulfilled $\begin{matrix}{{{\ldots \quad \omega_{1}} = \sqrt{\omega_{0}^{2} + \frac{K - \sqrt{K\left( {K + {4\omega_{0}^{2}}} \right)}}{2}}},} & \left( {{Exp}.\quad 2} \right) \\{{{\ldots \quad \omega_{2}} = \sqrt{\omega_{0}^{2} + \frac{K + \sqrt{K\left( {K + {4\omega_{0}^{2}}} \right)}}{2}}},} & \quad \\{{{\ldots \quad K} = \frac{M}{C_{0}^{2}R_{0}^{2}}},{{\ldots \quad M} = {\frac{R_{0}}{R_{c}} - 1}}} & \quad \\{{M > 0},{R_{0} > {R\quad c}}} & \quad \\{{\ldots \quad ._{T}} = \quad {{._{2}\quad {- \quad ._{1}}} = {\sqrt{\frac{K^{2}}{4._{0}^{2}} + K} = {\frac{._{0}}{2\quad Q_{0}}\sqrt{M\left( {{4\quad Q_{0}} + M} \right)}}}}} & \left( {{Exp}.\quad 3} \right)\end{matrix}$

T: unwanted resonance non-angular bandwidth $\begin{matrix}{{\ldots \quad Q} = {\frac{R_{0}}{._{0}L_{0}} = \quad {{._{0}C_{0}}R_{0}}}} & \left( {{Exp}.\quad 4} \right)\end{matrix}$

the (Exp. 1) represents unwanted resonance non-angular bandwidth, (Exp.2) represents a condition for fulfilling the (Exp. 1), and (Exp. 3)represents an unwanted band, (Exp. 5) is fulfilled, where$\begin{matrix}{{{{\ldots \quad R_{L}} = {{\frac{{{r.} \times C} - {R_{c} \times D}}{A^{2} + B^{2}}\quad \ldots \quad X_{L}} = {{{\frac{{{X.} \times C} - {X_{c} \times D}}{A^{2} + B^{2}}.\ldots}\quad {r.}} = \frac{R_{0}X_{0}^{2}}{R_{0}^{2} + X_{0}^{2}}}}},{{\ldots \quad {X.}} = \frac{X_{0}R_{0}^{2}}{R_{0}^{2} + X_{0}^{2}}},{{\ldots \quad X_{0}} = \frac{1}{\ldots \quad {C_{0}\left( {\frac{._{0}^{2}}{.^{2}} - 1} \right)}}},{{\ldots \quad X_{c}} = \frac{1}{\ldots \quad C_{c}}}}{{{\ldots \quad A} = {r.\quad {- \quad R_{c}}}},{{\ldots \quad B} = {X.\quad {- \quad X_{c}}}},{{\ldots \quad C} = {R_{c}^{2} + X_{c}^{2}}},{{\ldots \quad D} = {r.^{2}{+ {X.^{2}}}}}}} & \left( {{Exp}.\quad 5} \right)\end{matrix}$

Q represents resonance frequency which is a ratio of a real number toreactance shown by the ω₀ in the (Exp. 4), RL represents the negativeresistance for oscillating the series arm consisting of L1/C1/R0 of theoscillator, XL represents reactance, Cc represents circuit capacitanceof the oscillation circuit, and ω represents oscillation angularfrequency, and (Exp. 5) represents negative resistance and loadcapacitance for oscillating a series arm consisting of L1/C1/R0 of theoscillator.
 6. A high-frequency piezoelectric oscillator according toany one of claims 1, 2, 3, and 4, wherein the resistance within a rangeaccording to claim 5 is organized within an inductor, and the inductorhaving the inductor and the resistor integrated together is connected inparallel to the interelectrode capacitance C0 of the vibrator.